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2 2

δ bout (ω) = bout (ω) bout (ω)


e2iθ ’ 1 P (ω) C — (ω) bin (ω)
= 2 Re bin (’ω) .
(16.51)

Satisfying condition (i) would require the right side of this equation to vanish as an
identity in θ. The generic assumption (16.2) combined with the explicit forms of the
functions P (ω) and C (ω) makes this impossible; therefore, the ampli¬er is phase
sensitive.
This feature is a consequence of the fact that P (ω) and C (ω) are both nonzero, so

that the right side of eqn (16.46) depends jointly on bin (ω) and bin (’ω). A straight-
forward calculation shows that condition (ii) of Section 16.1.1 is also violated, even
for the simple case that the reservoir for the mirror M2 is the vacuum. Choosing an
appropriate de¬nition of the gain for a phase-sensitive ampli¬er is a bit trickier than
for the phase-insensitive cases, so this step will be postponed to the general treatment
in Section 16.4.
The alert reader will have noticed that the ampli¬ed signal is propagating back-
wards toward the source of the input signal. Devices of this kind are sometimes called
re¬‚ection ampli¬ers. This is not a useful feature for communications applications;
therefore, it is necessary to reverse the direction of the ampli¬er output so that it
propagates in the same direction as the input signal. Mirrors will not do for this task,
since they would interfere with the input. One solution is to redirect the ampli¬er
output by using an optical circulator, as described in Section 8.6. This device will
redirect the output signal, but it will not interfere with the input signal or add further
noise.
Linear optical ampli¬ers—
½¼

16.3 Traveling-wave ampli¬ers
The regenerative ampli¬ers discussed above enhance the nonlinear interaction for a
relatively weak cw pump beam by means of the resonant cavity formed by the mirrors
M1 and M2. This approach has the disadvantage of restricting the useful bandwidth to
that of the cavity. An alternative method is to remove the mirrors M1 and M2 to get
the con¬guration shown in Fig. 16.3, but this experimental simpli¬cation inevitably
comes at the expense of some theoretical complication.
The mirrors in the regenerative ampli¬ers perform two closely related functions.
The ¬rst is to guarantee that the ¬eld inside the cavity is a superposition of a discrete
set of cavity modes. In practice, the design parameters are chosen so that only one
cavity mode is excited. The position dependence of the ¬eld is then entirely given by
the corresponding mode function; in e¬ect, the cavity is a zero-dimensional system.
The second function”which follows from the ¬rst”is to justify the sample“reservoir
model that treats the discrete modes inside the cavity and the continuum of reservoir
modes outside the cavity as kinematically-independent degrees of freedom.
Removing the mirrors eliminates both of these conceptual simpli¬cations. Since
there are no discrete cavity modes, each of the continuum of external modes propagates
through the ampli¬er and interacts with the gain medium. Thus all ¬eld modes are
reservoir modes, and the sample consists of the atoms in the gain medium.
The interaction of the ¬eld with the gain medium could be treated by generalizing
the scattering description of passive, linear devices developed in Section 8.2, but this
approach would be quite complicated in the present application. The fact that the
sample occupies a ¬xed interval, say 0 z LS , along the propagation (z) axis
violates translation invariance and therefore conservation of momentum. Consequently,
the scattering matrix for the ampli¬er connects each incident plane wave, exp (ikz),
to a continuum of scattered waves exp (ik z).
We will avoid this complication by employing a position“space approach that
closely resembles the classical theory of parametric ampli¬cation (Yariv, 1989, Chap.
17). This technique can also be regarded as the Heisenberg-picture version of a method
developed to treat squeezing in a traveling-wave con¬guration (Deutsch and Garrison,
1991b).

16.3.1 Laser ampli¬er
As a concrete example, we consider a sample composed of a collection of three-level
atoms”with the level structure displayed in Fig. 16.4”which is made into a gain

Fig. 16.3 A black box schematic of a travel-
ing-wave ampli¬er. The shaded box indicates
the gain medium and the ¬elds at the two ports
are the input and output values of the signal.
The vacuum ¬‚uctuations entering port 2 are
not indicated, since they do not couple to the
signal.
½½
Traveling-wave ampli¬ers


3
ω32
Fig. 16.4 A three-level atom with a popula-
2
42 tion inversion between levels 1 and 2, main-
tained by an incoherent pump (dark double ar-
Signal
ω21 ω31 row) with rate RP . The solid arrow, the dashed
arrow, and the wavy arrows respectively rep-
resent the ampli¬ed signal transition, a nonra-
1 diative decay, and spontaneous emission.


medium by maintaining a population inversion between levels 1 and 2 through the
use of the incoherent pumping mechanism described in Section 14.5. By virtue of
the cylindrical shape of the gain medium, the end-¬re modes”i.e. ¬eld modes with
frequencies ω ω21 and propagation vectors, k, lying in a narrow cone around the
axis of the cylinder”will be preferentially ampli¬ed.
This new feature requires a modi¬cation of the reservoir assignment used for the
pumping calculation. The noise reservoir previously associated with the spontaneous
emission 2 ’ 1 is replaced by two reservoirs: (1) a noise reservoir associated with
spontaneous emission into modes with propagation vectors outside the end-¬re cone;
and (2) a signal reservoir associated with the end-¬re modes.
In the undepleted pump approximation, the back action of the atoms on the pump
¬eld can be ignored. This certainly cannot be done for the interaction with the signal
reservoir; after all, the action of the gain medium on the signal is the whole purpose of
the device. Thus the coupling of the entire collection of atoms to the signal reservoir
must be included by using the interaction Hamiltonian
(n)
HS1 = ’ S21 (t) d21 · E(+) (rn , t) + HC , (16.52)
n

where the sum runs over the atoms in the sample and the coordinate, rn , of the nth
atom is treated classically.
The description of the signal reservoir given above amounts to the assumption that
the Heisenberg-picture density operator for the input signal is a paraxial state with
respect to the z-axis; consequently, the contribution of the end-¬re modes to the ¬eld
operator can be represented in terms of the slowly-varying envelope operators φs (r, t)
appearing in eqn (7.33). We will assume that the ampli¬er has been designed so that
only one polarization will be ampli¬ed; consequently, only one operator φ (r, t) will be
needed.
Turning next to the input signal, we recall that a paraxial state is characterized
by transverse and longitudinal length scales Λ = 1/ (θk0 ) and Λ = 1/ θ2 k0 re-
spectively, where θ is the opening angle of the paraxial ray bundle. The scale lengths
Λ and Λ correspond respectively to the spot size and Rayleigh range of a classical
Gaussian beam. We choose θ so that Λ > 2RS and Λ LS , where RS and LS are
respectively the radius and length of the cylinder. This allows a further simpli¬cation
in which di¬raction is ignored and the envelope operator is approximated by
Linear optical ampli¬ers—
½¾

1
φ (r, t) = √ φ (z, t) , (16.53)
σ
2
where σ = πRS . In this 1D approximation, the ¬eld expansion (7.33) and the commu-
tation relation (7.35) are respectively replaced by

ω0 (vg0 /c)
E(+) (r, t) = i e0 φ (z, t) ei(k0 z’ω0 t) (16.54)
2 0 n0 σ
and
φ (z, t) , φ† (z , t) = δ (z ’ z ) . (16.55)
The discretely distributed atoms and the continuous ¬eld are placed on a more
even footing by introducing the spatially coarse-grained operator density
1
Sqp (t) χ (z ’ zn ) .
(n)
Sqp (z, t) = (16.56)
∆z n
The averaging interval ∆z is chosen to satisfy the following two conditions. (1) A slab
with volume σ∆z contains many atoms. (2) The envelope operator φ (z, t) is essentially
constant over an interval of length ∆z. The function
χ (z ’ zn ) = θ (∆z/2 ’ z + zn ) θ (z ’ zn + ∆z/2) (16.57)
serves to con¬ne the n-sum to the atoms in a slab of thickness ∆z centered at z. The
atomic envelope operators are de¬ned by
Sqp (z, t) = S qp (z, t) eiωqp t ei[ψq (z,t)’ψp (z,t)] , (16.58)
where the phases satisfy
ψ2 (z, t) ’ ψ1 (z, t) = ∆0 t ’ k0 z . (16.59)
Using this notation, together with eqn (16.54), allows us to rewrite eqn (16.52) as
LS
HS1 = ’i dz f S 21 (z, t) φ (z, t) ’ HC , (16.60)
0
where
(vg0 /c) ω0 d21 · e0
f≡ (16.61)
2 0σ
is the coupling constant.
The total electromagnetic part of the Hamiltonian for this 1D model is, therefore,

dzφ† (z, t) vg0 ∇z φ (z, t) + HS1 .
Hem = (16.62)
i
’∞
This leads to the corresponding Heisenberg equation
‚ ‚
φ (z, t) = f— S 12 (z, t) for 0
+ vg0 z LS , (16.63)
‚t ‚z
‚ ‚
+ vg0 φ (z, t) = 0 for z < 0 or z > LS (16.64)
‚t ‚z
for the ¬eld.
½¿
Traveling-wave ampli¬ers

The atomic operators are coupled to the reservoirs describing the incoherent pump
and spontaneous emission into o¬-axis modes; therefore, we insert eqn (16.60) into the
coarse-grained version of eqn (14.177) to ¬nd
d
S 12 (z, t) = [i∆0 ’ “12 ] S 12 (z, t) ’ f S 11 (z, t) ’ S 22 (z, t) φ (z, t) + ξ12 (z, t) .
dt
(16.65)
The coarse-grained noise operator
1 (n)
ξ12 (t) χ (z ’ zn )
ξ12 (z, t) = (16.66)
∆z n

has the correlation function

ξ12 (z, t) ξ12 (z , t ) = nat σC12,12 δ (t ’ t ) δ (z ’ z ) , (16.67)

where δ (z ’ z ) is a coarse-grained delta function, nat is the density of atoms, and
C12,12 is an element of the noise correlation matrix discussed in Section 14.6.2.
In the strong-pump limit, the dephasing rate “12 = (w21 + RP ) /2 is large com-
pared to the other terms in eqn (16.65); therefore, applying the adiabatic elimination
rule (11.187) provides the approximate solution

S 22 (z, t) ’ S 11 (z, t) ξ12 (z, t)
S 12 (z, t) = f φ (z, t) + . (16.68)
“12 ’ i∆0 “12 ’ i∆0
We have to warn the reader that this procedure is something of a swindle, since
ξ12 (z, t) is not a slowly-varying function of t. Fortunately, the result can be justi¬ed”
see Exercise 16.3”by interpreting δ (t ’ t ) in eqn (16.67) as an even coarser-grained
delta function, that only acts on test functions that vary slowly on the dephasing time
scale T12 = 1/“12 .
In the linear approximation for eqn (16.68), the operator S 22 (z, t) ’ S 11 (z, t) can
be simpli¬ed in two ways. The ¬rst is to neglect the small quantum ¬‚uctuations,
i.e. to replace the operator by its average S 22 (z, t) ’ S 11 (z, t) . The next step is to
solve the averaged form of the operator Bloch equations (14.174)“(14.177), with the
approximation that HS1 = 0. The result is

S 22 (z, t) ’ S 11 (z, t) ≈ S 22 (z, t) ’ S 11 (z, t) = nat σD , (16.69)

where D is the steady-state inversion for a single atom. With these approximations,
the propagation equation (16.63) becomes

f—
2
|f| nat σD
‚ ‚
+ vg0 φ (z, t) = φ (z, t) + ξ12 (z, t) . (16.70)
“12 ’ i∆0 “12 ’ i∆0
‚t ‚z

This equation is readily solved by transforming to the wave coordinates:

„ = t ’ z/vg0 (the retarded time for the signal wave) ,
(16.71)
z = z,
Linear optical ampli¬ers—
½

to get
f—

φ (z, „ ) = gφ (z, „ ) + ξ12 (z, „ ) , (16.72)
vg0 (“12 ’ i∆0 )
‚z
where
|f|2 nat σD k0 |d21 · e0 |2 nat D
g= = (16.73)
vg0 [“12 ’ i∆0 ] 2 0 [“12 ’ i∆0 ]
is the (complex) small-signal gain. The retarded time „ can be treated as a parameter
in eqn (16.72), so the solution is
z
f—
gz
dz1 eg(z’z1 ) ξ12 (z1 , „ ) ,
φ (z, „ ) = φ (0, „ ) e + (16.74)
vg0 (“12 ’ i∆0 ) 0

which has the form
f— z ’ z1
z
φ (z, t) = φ (0, t ’ z/vg0 ) e dz1 eg(z’z1 ) ξ12 z1 , t ’
gz
+
vg0 (“12 ’ i∆0 ) vg0
0
(16.75)
in the laboratory coordinates (z, t).
Setting z = LS and letting t ’ t + LS /vg0 gives the ¬eld value at the output face:

f— LS
z1
gLS
dz1 eg(z’z1 ) ξ12 z1 , t +
φ (LS , t + LS /vg0 ) = φ (0, t) e + .
vg0 (“12 ’ i∆0 ) vg0
0
(16.76)
In order to recover the standard form for input“output relations we introduce the
representations
1 dω
bin (ω) e’iω(t’z/vg0 ) for z < 0
φ (z, t) = √ (16.77)
vg0 2π

and
1 dω
bout (ω) e’iω(t’z/vg0 ) for z > LS ,
φ (z, t) = √ (16.78)
vg0 2π

for the solutions of eqn (16.64) outside the crystal. The factor 1/ vg0 is inserted to
guarantee that the commutation relation (16.55) for φ (z, t) and the standard input“
output commutation relations

bγ (ω) , b† (ω ) = 2πδ (ω ’ ω ) (γ = in, out) (16.79)
γ

are both satis¬ed. Substituting eqns (16.77) and (16.78) into eqn (16.76) and carrying
out a Fourier transform produces the input“output relation

bout (ω) = egLS bin (ω) + · (ω) , (16.80)

where
f— LS
dz1 eg(z’z1 ) e’iωz1 /vg0 ξ12 (z1 , ω)
· (ω) = √ (16.81)
vg0 (“12 ’ i∆0 ) 0
½
Traveling-wave ampli¬ers

is the ampli¬er noise operator. By using the frequency-domain form of eqn (16.67),
one can show that the noise correlation function is
1
· (ω) · † (ω ) + · † (ω) · (ω )
Kamp (ω, ω ) =
2
= Namp 2πδ (ω ’ ω ) , (16.82)

where the noise strength is
2
nat k0 |d21 · e0 | e2gLS ’ 1 1
Namp = (C12,12 + C21,21 ) . (16.83)
2 0 (“2 + ∆2 ) 2g 2
12 0

Comparing eqn (16.80) to eqn (16.46) shows that P (ω) = egLS and C (ω) = 0. Con-
sequently, this ampli¬er is phase insensitive and phase transmitting.

16.3.2 Traveling-wave OPA
For this example, we return to the down-conversion technique by removing the mir-
rors from the phase-sensitive design shown in Fig. 16.2. Even without the mirrors,
appropriately cutting the ends of the crystal will guarantee that the pump beam and
the degenerate signal and idler beams copropagate along the length of the crystal. We
assume a Gaussian pump beam with spot size w0 and Rayleigh range ZR focussed on
a nonlinear crystal with radius RS and length LS .
If w0 > 2RS and ZR LS , the e¬ects of di¬raction are negligible; consequently,
the problem is e¬ectively one-dimensional. In this limit, the classical pump ¬eld can
be expressed as

E P (r, t) = eP |EP 0 | eiθP fP (t ’ z/vgP ) ei(kP z’ωP t) , (16.84)

where we have assumed that the medium outside the crystal is linearly index matched.
The temporal shape of the pump pulse is described by the function fP („ ), with max-
imum value fP (0) = 1 and pulse duration „P . In the long-pulse limit, „P ’ ∞, the
problem is further simpli¬ed by setting fP (t ’ z/vgP ) = 1.
In the 1D limit the signal“idler mode is described by a paraxial state, so the
¬eld can again be represented by eqn (16.54), with ω0 = ωP /2. The polarization of
the signal“idler mode is ¬xed, relative to that of the pump, by the phase-matching
conditions in the nonlinear crystal. Applying the 1D approximation and the long-pulse
limit to the expressions (7.39) and (13.30) yields the e¬ective ¬eld Hamiltonian
∞ LS

dz e’iθP φ2 (z, t) + HC . (16.85)
dzφ (z, t) vg0 ∇z φ (z, t) + g (3)
Hem =
i 2
’∞ 0

The special form of the interaction Hamiltonian”which represents the pair-produc-
tion aspect of down-conversion”produces a propagation equation

‚ ‚
φ (z, t) = ’ig (3) eiθP φ† (z, t)
+ vg0 (16.86)
‚t ‚z
Linear optical ampli¬ers—
½

that couples the ¬eld φ (z, t) to its adjoint φ† (z, t). This means that the propagation
equation and its adjoint must be solved together. In the wave coordinates de¬ned by
eqn (16.71) the equations to be solved are


φ (z, „ ) = ’igeiθP φ† (z, „ ) , (16.87)
‚z

‚†
φ (z, „ ) = ige’iθP φ (z, „ ) , (16.88)
‚z
where g = g (3) /vg0 is the weak signal gain. Since the retarded time „ only appears as
a parameter, these equations can be solved by standard techniques to ¬nd

φ (z, t) = φ (0, t ’ z/vg0 ) cosh (gz) ’ ieiθP φ† (0, t ’ z/vg0 ) sinh (gz) , (16.89)

where we have reverted to the original (z, t)-variables. Thus the solution at z, t is
expressed in terms of the ¬eld operators evaluated at the input face, z = 0, and the
retarded time „ = t ’ z/vg0 .
The time-domain, input“output relation for the traveling-wave ampli¬er is obtained
by evaluating this solution at the output face, z = LS , and letting t ’ t + LS /vg0 :

φ (LS , t + LS /vg0 ) = φ (0, t) cosh (gLS ) ’ ieiθP φ† (0, t) sinh (gLS ) . (16.90)

Fourier transforming this equation yields

e’iLS /vg0 φ (LS , ω) = φ (0, ω) cosh (gLS ) ’ ieiθP φ† (0, ’ω) sinh (gLS ) , (16.91)

which can be brought into the standard form for input“output relations by using the
representations (16.77) and (16.78) to ¬nd

bout (ω) = P bin (ω) ’ ieiθP Cb† (0, ’ω) , (16.92)
in

with
P = cosh (gLS ) and C = sinh (gLS ) . (16.93)

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